Broadband Modified Proximity Coupled Patch Antenna with Cavity-Backed Configuration

Article information

J Electromagn Eng Sci. 2021;21(1):8-14
Publication date (electronic) : 2021 January 31
doi : https://doi.org/10.26866/jees.2021.21.1.8
1The 1st R&D Institute, Agency for Defense Development, Daejeon, Korea
2Electrical and Electronic Engineering Department, Yonsei University, Seoul, Korea
*Corresponding Author: Young Joong Yoon (e-mail: yjyoon@yonsei.ac.kr)
Received 2020 February 28; Revised 2020 July 5; Accepted 2020 August 31.

Abstract

A modified proximity-coupled microstrip patch antenna with broad impedance bandwidth is proposed by incorporating proximity-coupled patch antenna into the rectangular open-ended microstrip feed line on a cavity structure. First we design a proximity-coupled microstrip antenna to have a wide bandwidth in the lower band centered at 7 GHz using a cavity-backed ground. To broaden the bandwidth of the antenna to the upper band, we then apply a rectangular open-ended microstrip feed line, adjusting the relative position to the cavity to generate an additional resonance close to 10 GHz. The combination of lower and upper band design results in a broadband antenna with dimensions of 30 mm × 30 mm × 9 mm (0.9λ0 × 0.9λ0 × 0.27λ0) is designed where λ0 corresponds to the free space wavelength at a center frequency of 9 GHz. The measurement results verify the broad impedance bandwidth (VSWR ≤ 2) of the antenna at 77% (5.6–12.6 GHz) while the broadside gain is maintained between 6 dBi and 8 dBi within the operational broad bandwidth.

I. Introduction

Microstrip patch antennas have been widely employed in wireless communication systems, mainly owing to their low cost, low profile, and easy fabrication. However, patch antennas usually have the disadvantage of a narrow bandwidth.

A proximity-coupled microstrip patch antenna has broadband characteristics compared to the probe-fed and edge-fed coupling methods. In the proximity-coupled microstrip configuration, the bandwidth can be increased by 10%–26% using a stacked radiator, L-probe feeding, and slot patch using stubs [14].

Placing the cavity-backed ground under the patch improves the bandwidth by reducing the surface wave and lowering the equivalent dielectric constant. Many microstrip antennas have been designed and studied on cavity structures to increase bandwidth [512]. In [6], a stacked patch with a cavity-backed ground plane enhanced the impedance matching and improved the bandwidth to 26%. In [11], a narrow cavity was used to create an efficient coupling of patches with thick substrates, and the bandwidth was increased to 40% by increasing the coupling amount.

In [12], a cavity-backed patch antenna with proximity coupling fed using a conventional microstrip feed line is presented that achieves 69.6% voltage standing wave ratio (VSWR) bandwidth. There are three substrate layers and its height corresponds to 0.38λ0, where λ0 denotes the wavelength of the operational center frequency.

In this paper, we propose a broadband cavity-backed proximity-coupled patch antenna on two substrate layers modified with a rectangular open-ended microstrip feed line (OEMF). The rectangular OEMF is defined as the combination of a rectangular patch and microstrip feed line. The rectangular OEMF technique can maintain the bandwidth and generate additional resonances to create a bandwidth expansion effect compared to those of conventional microstrip feed line. The proximity-coupled patch and rectangular OEMF are placed on upper and lower substrates on a cavity structure to generate multiple resonances in different frequency bands. The rectangular OEMF on the lower layer is designed to achieve an upper band VSWR bandwidth through the coupling with the cavity. The upper layer patch fed by the rectangular OEMF with the cavity realizes the lower band VSWR bandwidth. As a result, the proposed antenna realizes 77% VSWR bandwidth from 5.6 GHz to 12.6 GHz with the dimensions of 0.9λ0 × 0.9λ0 × 0.27λ0 (width × length × height), where λ0 corresponds to the free space wavelength of 9 GHz.

II. Antenna Design

The geometry and parameters of the antenna are shown in Fig. 1. The antenna consists of a patch, substrate 1 and 2, a rectangular OEMF, and a cavity-backed structure.

Fig. 1

Antenna configuration. (a) 3D shape and (b) top view.

The dimensions of the patch are W2x × L2y and it is placed on the substrate 2 at height h2. The antenna is fed through proximity coupling between the patch and the rectangular OEMF. The rectangular OEMF has a size of W1x × L1y, and the length of the feed line is Ly. The length between the cavity starting point and ground end on the y axis is Lc. A ground plane with a cavity is placed below substrate 1. The antenna parameters were ɛr1 = ɛr2 = 2.2, W2x = 13.72 mm, L2y = 7.25 mm, h1 = 0.508 mm, h2 = 3.175 mm, W1x = 7 mm, L1y = 6.25 mm, Ly = 9 mm, Lc = 9 mm, Wcx = 11.65 mm, Lcy = 26.58 mm, and Hcz = 3.74 mm.

Variations of the design parameters of the cavity, patch and rectangular OEMF affect the input impedance and resonant frequency of the antenna. In the following parameter study, only a rectangular OEMF and the parameter of focus are varied, and the remaining parameters are maintained as presented above.

Fig. 2 shows the variation of input impedance and reflection coefficient when the length of the rectangular OEMF(Ly) is changed. In case of Ly > Lc, upper and lower resonances occur, but the impedance between the two resonances is not matched to 50 Ω. In the case of Ly = Lc, the impedance is roughly 50 Ω and the impedance variation is small, which means that broadband matching occurs. In the case of Ly < Lc, a single resonance occurs near 9 GHz, and the resistance in the other frequencies is smaller than 50 Ω and the variation of the reactance increases. Consequently, the broadband matching is broken. S11 also has the largest bandwidth when Ly = Lc.

Fig. 2

Input impedance and reflection coefficient of the antenna with variation of length of the rectangular OEMF(Ly): (a) resistance, (b) reactance, and (c) reflection coefficient.

Variations of input impedance when all parameters are the same and only L1y is changed, meaning the length of the y-direction of the rectangular OEMF when the end of the rectangular OEMF is aligned with the center of the top patch, are shown in Fig. 3. It can be seen that when L1y is 6 mm, S11 has the widest bandwidth characteristic. When L1y is larger than 6 mm, a single resonance occurs. As L1y becomes smaller, the resonance peak decreases. It can be seen that broadband matching occurs when the end of the cavity and the starting point of the rectangular open ended microstrip coincide on the y-axis (L1y = 6 mm).

Fig. 3

Input impedance and reflection coefficient of the antenna with variation of size of the rectangular OEMF(L1y): (a) resistance, (b) reactance, and (c) reflection coefficient.

Fig. 4 shows the change in reflection coefficients when the dimension of the cavity is varied. As Lcy became larger, broadband matching occurred. Wcx showed a bandwidth increase when it was increased to 12 mm. Hcz exhibited good bandwidth at about 4 mm and when Hcz was too low, bandwidth was significantly reduced. It can be seen in Fig. 4 that additional resonance in the upper frequency band occurs, especially when the cavity is large (Lcy ≥ 26 mm, Wcx ≥ 11.5 mm, Hcz ≥ 3 mm).

Fig. 4

Reflection coefficients of the antenna with different sizes of cavity: (a) Lcy, (b) Wcx, and (c) Hcz.

Fig. 5 shows results of S11 for the structure with only the patch, only the rectangular OEMF, and the whole proposed structure. The antenna with only the patch is for the structure where only the narrow feed line is extended with the same length. Only the rectangular OEMF is for the structure without the patch and the substrate 2. The S11 characteristic of the structure with only the patch (W1x = 1.8 mm) has a bandwidth of approximately 26% in the low band of 6 to 9 GHz, which shows the bandwidth performance when the cavity is coupled to the proximity-coupled antenna. The S11 characteristic of the structure with only the rectangular OEMF (W2x = 0 mm) has a bandwidth of approximately 20% in the high band of 9 to 12 GHz, which shows the bandwidth expansion effect of the rectangular OEMF on the entire structure. The rectangular OEMF allows additional bandwidth to be secured while maintaining the existing bandwidth. The S11 characteristics of the proposed structure are shown by combining the characteristics of the structure with only the patch and the structure with only the rectangular OEMF. Because the proximity-coupled microstrip antenna with cavity-acked structure mainly operates at the lower band and the added rectangular OEMF as a modified feed line mainly operates at the upper band, the combination of the two structures eventually increases the bandwidth.

Fig. 5

Simulated reflection coefficient of the antenna with different structures.

It can be seen that a bandwidth of approximately 77% is realized from 5.6 to 12.6 GHz. It can be observed that VSWR bandwidth is almost doubled compared with the conventional method [12]. All the simulations were performed using the commercial software Computer Simulation Technology (CST) Microwave Studio.

Electric field distributions on the y-z plane show the status of the resonance of patch and rectangular OEMF depending on the frequency variation. The simulated field distributions for the three frequencies in the side view are shown in Fig. 6. In the case of 6.4 GHz and 7.4 GHz, it can be seen that resonance mainly occurs in the patch. In the case of 10.1 GHz and 11.8 GHz, it can be seen that resonance occurs mainly in the rectangular OEMF, and very weak resonance occurs in the patch.

Fig. 6

Electric field distribution in the y-z plane depending on frequency: (a) 6.4 GHz, (b) 7.4 GHz, (c) 10.1 GHz, and (d) 11.8 GHz.

III. Fabrication and Measurement Results

An antenna prototype was fabricated as shown in Fig. 7. To connect a coaxial connector, additional housing with aluminum was added to the side of the antenna, which only negligibly affects the antenna performance.

Fig. 7

Prototype of the proposed antenna (a) and cavity structure (b).

The simulation and measurement results of the co-polarization patterns at 6, 8, 10, and 12 GHz for E-plane and H-plane are presented in Fig. 8. The measured results were found to be consistent with the simulated ones. The asymmetry of the E-plane radiation pattern gradually tends to increase with the increase in frequency.

Fig. 8

Measured and simulated radiation patterns of the antenna at different frequencies: (a) E-plane (6, 8 GHz), (b) E-plane (10, 12 GHz), (c) H-plane (6, 8 GHz), and (d) H-plane (10, 12 GHz).

At 12 GHz, a null is generated in approximately 60° direction, which causes a narrowing of the antenna beam width. The radiation pattern was found to be distorted due to the physical asymmetry of the antenna on the z-y plane.

As shown in Fig. 9, the VSWR was simulated and measured. The VSWR bandwidth was measured to be more than 77% for the proposed antenna. The measured result was consistent with the simulated one.

Fig. 9

Simulated and measured VSWRs for the proposed antenna.

Fig. 10 shows the measured gains of the proposed antenna. A reasonably good radiation gain from 6 dBi to 8 dBi is obtained within the entire operating band.

Fig. 10

Measured gain of the proposed antenna.

IV. Conclusion

This paper proposed a broadband modified cavity-backed proximity-coupled microstrip patch. The patch was designed to resonate with the cavity in the lower band and the rectangular OEMF to resonate with the cavity in the upper band, resulting in a bandwidth as high as 77% (VSWR ≤ 2.0) across a frequency range of 5.6 to 12.6 GHz. The proposed antenna configuration with a cavity-backed ground plane is easy to fabricate and is expected to be applicable to wideband array antennas.

References

1. Rowe WS, Waterhouse RB. Investigation into the performance of proximity coupled stacked patches. IEEE Transactions on Antennas and Propagation 54(6):1693–1698. 2006;
2. Guo YX, Mak CL, Luk KM, Lee KF. Analysis and design of L-probe proximity fed-patch antennas. IEEE Transactions on Antennas and Propagation 49(2):145–149. 2001;
3. Qu SW, Xue Q. A Y-shaped stub proximity coupled V-slot microstrip patch antenna. IEEE Antennas and Wireless Propagation Letters 6:40–42. 2007;
4. Ooi BL. A double-π stub proximity feed U-slot patch antenna. IEEE Transactions on Antennas and Propagation 52(9):2491–2496. 2004;
5. Elmezughi AS, Rowe WST, Waterhouse RB. Cavity backed hi-lo stacked patch antennas. In : Proceedings of 2008 IEEE Antennas and Propagation Society International Symposium. San Diego, CA; 2008; p. 2301–2034.
6. Song XD, Lu XP, Wei W. A single-layer wideband cavity-backed microstrip patch antenna. In : Proceedings of 2015 IEEE International Symposium on Antennas and Propagation & USNC/URSI National Radio Science Meeting. Vancouver, Canada; 2015; p. 2425–2426.
7. Wang Y, Zhu F, Gao S. Compact cavity-backed patch antenna with wideband bandwidth using parasitic patch. In : Proceedings of 2017 6th Asia-Pacific Conference on Antennas and Propagation (APCAP). Xi’an, China; 2017; p. 1–3.
8. Zhu J, Chu CH, Deng L, Zhang C, Yang Y, Li S. mm-Wave high gain cavity-backed aperture-coupled patch antenna array. IEEE Access 6:44050–44058. 2018;
9. Xia RL, Qu SW, Yang S, Chen Y. Wideband widescanning phased array with connected backed cavities and parasitic striplines. IEEE Transactions on Antennas and Propagation 66(4):1767–1775. 2018;
10. Liu Y, Chen S, Ren Y, Cheng J, Liu QH. A broadband proximity-coupled dual-polarized microstrip antenna with L-shape backed cavity for X-band applications. AEU-International Journal of Electronics and Communications 69(9):1226–1232. 2015;
11. Sun D, You L. A broadband impedance matching method for proximity-coupled microstrip antenna. IEEE Transactions on Antennas and Propagation 58(4):1392–1397. 2010;
12. Sun D, Dou W, You L, Yan X, Shen R. A broadband proximity-coupled stacked microstrip antenna with cavity-backed configuration. IEEE Antennas and Wireless Propagation Letters 10:1055–1058. 2011;

Biography

Deok Kyu Kong received his B.S. and M.S. degrees in electrical and computer engineering from Ajou University, Suwon, Korea in 1994 and 1996, respectively. He joined the Agency for Defense Development, Daejeon, Korea, in 1996, where he is currently a Principal Researcher. His current research interests include wideband antennas and direction-finding antennas.

Jaesik Kim received B.S. degree in radio wave engineering from Kwangwoon University Seoul, Korea in 2011 and a Ph.D. degree in electrical and electronic engineering from Yonsei University, Seoul, Korea in 2017. He joined the Agency for Defense Development, Daejeon, Korea in 2017, where he is currently a Senior Researcher. His current research interests include direction-finding antennas and phased array antennas.

Daewoong Woo received B.S. degree in electronic and electrical engineering from Kyungpook National University, Daegu in 2007, and a Ph.D. degree in electrical engineering from Pohang University of Science and Technology (POSTECH), Pohang, Korea, in 2013. He joined the Agency for Defense Development, Daejeon, Korea, in 2013, where he is currently a Senior Researcher. His current research interests include phased array antennas, slot array antennas, periodic structures and direction-finding.

Young Joong Yoon received B.S. and M.S. degrees in electronic engineering from Yonsei University, Seoul, Korea, in 1981 and 1986, and a Ph.D. in electrical engineering from the Georgia Institute of Technology, Atlanta, in 1991. In 1993, he joined the Department of Electrical and Electronic Engineering, Yonsei University, where he is currently a Professor of Electromagnetics. His main research interests are related to microwave theory, small antennas, high-power electromagnetics, and radio propagation.

Article information Continued

Fig. 1

Antenna configuration. (a) 3D shape and (b) top view.

Fig. 2

Input impedance and reflection coefficient of the antenna with variation of length of the rectangular OEMF(Ly): (a) resistance, (b) reactance, and (c) reflection coefficient.

Fig. 3

Input impedance and reflection coefficient of the antenna with variation of size of the rectangular OEMF(L1y): (a) resistance, (b) reactance, and (c) reflection coefficient.

Fig. 4

Reflection coefficients of the antenna with different sizes of cavity: (a) Lcy, (b) Wcx, and (c) Hcz.

Fig. 5

Simulated reflection coefficient of the antenna with different structures.

Fig. 6

Electric field distribution in the y-z plane depending on frequency: (a) 6.4 GHz, (b) 7.4 GHz, (c) 10.1 GHz, and (d) 11.8 GHz.

Fig. 7

Prototype of the proposed antenna (a) and cavity structure (b).

Fig. 8

Measured and simulated radiation patterns of the antenna at different frequencies: (a) E-plane (6, 8 GHz), (b) E-plane (10, 12 GHz), (c) H-plane (6, 8 GHz), and (d) H-plane (10, 12 GHz).

Fig. 9

Simulated and measured VSWRs for the proposed antenna.

Fig. 10

Measured gain of the proposed antenna.